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400 MHz to 6 GHz Quadrature Demodulator ADL5380
FEATURES
Operating RF and LO frequency: 400 MHz to 6 GHz Input IP3 30 dBm @ 900 MHz 28 dBm @1900 MHz Input IP2: >65 dBm @ 900 MHz Input P1dB (IP1dB): 11.6 dBm @ 900 MHz Noise figure (NF) 10.9 dB @ 900 MHz 11.7 dB @ 1900 MHz Voltage conversion gain: ~7 dB Quadrature demodulation accuracy @ 900 MHz Phase accuracy: ~0.2 Amplitude balance: ~0.07 dB Demodulation bandwidth: ~390 MHz Baseband I/Q drive: 2 V p-p into 200 Single 5 V supply
FUNCTIONAL BLOCK DIAGRAM
ENBL ADJ
ADL5380
BIAS
IHI
ILO
LOIP RFIN V2I RFIP QUADRATURE PHASE SPLITTER LOIN QHI
Figure 1.
APPLICATIONS
Cellular W-CDMA/GSM/LTE Microwave point-to-(multi)point radios Broadband wireless and WiMAX
GENERAL DESCRIPTION
The ADL5380 is a broadband quadrature I-Q demodulator that covers an RF/IF input frequency range from 400 MHz to 6 GHz. With a NF = 10.9 dB, IP1dB = 11.6 dBm, and IIP3 = 29.7 dBm @ 900 MHz, the ADL5380 demodulator offers outstanding dynamic range suitable for the demanding infrastructure direct-conversion requirements. The differential RF inputs provide a well-behaved broadband input impedance of 50 and are best driven from a 1:1 balun for optimum performance. Excellent demodulation accuracy is achieved with amplitude and phase balances of ~0.07 dB and ~0.2, respectively. The demodulated in-phase (I) and quadrature (Q) differential outputs are fully buffered and provide a voltage conversion gain of ~7 dB. The buffered baseband outputs are capable of driving a 2 V p-p differential signal into 200 . The fully balanced design minimizes effects from second-order distortion. The leakage from the LO port to the RF port is <-50 dBm. Differential dc offsets at the I and Q outputs are typically <20 mV. Both of these factors contribute to the excellent IIP2 specification, which is >65 dBm. The ADL5380 operates off a single 4.75 V to 5.25 V supply. The supply current is adjustable by placing an external resistor from the ADJ pin to either the positive supply, VS, (to increase supply current and improve IIP3) or to ground (which decreases supply current at the expense of IIP3). The ADL5380 is fabricated using the Analog Devices, Inc., advanced silicon-germanium bipolar process and is available in a 24-lead exposed paddle LFCSP.
Rev. 0
Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. Specifications subject to change without notice. No license is granted by implication or otherwise under any patent or patent rights of Analog Devices. Trademarks and registered trademarks are the property of their respective owners.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A. Tel: 781.329.4700 www.analog.com Fax: 781.461.3113 (c)2009 Analog Devices, Inc. All rights reserved.
07585-001
QLO
ADL5380 TABLE OF CONTENTS
Features .............................................................................................. 1 Applications ....................................................................................... 1 Functional Block Diagram .............................................................. 1 General Description ......................................................................... 1 Revision History ............................................................................... 2 Specifications..................................................................................... 3 Absolute Maximum Ratings............................................................ 5 ESD Caution .................................................................................. 5 Pin Configuration and Function Descriptions ............................. 6 Typical Performance Characteristics ............................................. 7 Low Band Operation .................................................................... 7 Midband Operation ................................................................... 11 High Band Operation ................................................................ 14 Distributions for fLO = 900 MHz ............................................... 17 Distributions for fLO = 1900 MHz............................................. 18 Distributions for fLO = 2700 MHz............................................. 19 Distributions for fLO = 3600 MHz............................................. 20 Distributions for fLO = 5800 MHz............................................. 21 Circuit Description ......................................................................... 22 LO Interface................................................................................. 22 V-to-I Converter ......................................................................... 22 Mixers .......................................................................................... 22 Emitter Follower Buffers ........................................................... 22 Bias Circuit .................................................................................. 22 Applications Information .............................................................. 23 Basic Connections ...................................................................... 23 Power Supply............................................................................... 23 Local Oscillator (LO) Input ...................................................... 23 RF Input ....................................................................................... 24 Baseband Outputs ...................................................................... 24 Error Vector Magnitude (EVM) Performance ........................... 24 Low IF Image Rejection............................................................. 25 Example Baseband Interface ..................................................... 26 Characterization Setups ................................................................. 30 Evaluation Board ............................................................................ 32 Thermal Grounding and Evaluation Board Layout............... 34 Outline Dimensions ....................................................................... 35 Ordering Guide .......................................................................... 35
REVISION HISTORY
7/09--Revision 0: Initial Version
Rev. 0 | Page 2 of 36
ADL5380 SPECIFICATIONS
VS = 5 V, TA = 25C, fLO = 900 MHz, fIF = 4.5 MHz, PLO = 0 dBm, ZO = 50 , unless otherwise noted. Baseband outputs differentially loaded with 450 . Loss of the balun used to drive the RF port was de-embedded from these measurements. Table 1.
Parameter OPERATING CONDITIONS LO and RF Frequency Range LO INPUT Input Return Loss LO Input Level I/Q BASEBAND OUTPUTS Voltage Conversion Gain Demodulation Bandwidth Quadrature Phase Error I/Q Amplitude Imbalance Output DC Offset (Differential) Output Common Mode Condition Min 0.4 LOIP, LOIN LO driven differentially through a balun at 900 MHz -6 QHI, QLO, IHI, ILO 450 differential load on I and Q outputs at 900 MHz 200 differential load on I and Q outputs at 900 MHz 1 V p-p signal, 3 dB bandwidth At 900 MHz 0 dBm LO input at 900 MHz Dependent on ADJ pin setting VADJ ~ 4 V (set by 1.5 k from ADJ pin to VS) VADJ ~ 4.8 V (set by 200 from ADJ pin to VS) VADJ ~ 2.4 V (ADJ pin open) Differential 200 load Each pin VS = VCC1, VCC2, VCC3 4.75 1.5 k from ADJ pin to VS; ENBL pin low 1.5 k from ADJ pin to VS; ENBL pin high Pin ENBL ENBL high to low ENBL low to high 2.5 1.7 VADJ ~ 4 V (set by 1.5 k from ADJ pin to VS) 6.9 11.6 -19 68 29.7 -52 -67 0.07 0.2 10.9 13.1 dB dBm dB dBm dBm dBm dBc dB Degrees dB dB 245 145 -70 45 950 -10 0 6.9 5.9 390 0.2 0.07 10 VS - 2.5 VS - 2.8 VS - 1.2 37 2 12 5.25 Typ Max 6 Unit GHz dB dBm dB dB MHz Degrees dB mV V V V MHz V p-p mA V mA mA dB ns ns V V
+6
0.1 dB Gain Flatness Output Swing Peak Output Current POWER SUPPLIES Voltage Current ENABLE FUNCTION Off Isolation Turn-On Settling Time Turn-Off Settling Time ENBL High Level (Logic 1) ENBL Low Level (Logic 0) DYNAMIC PERFORMANCE at RF = 900 MHz Conversion Gain Input P1dB RF Input Return Loss Second-Order Input Intercept (IIP2) Third-Order Input Intercept (IIP3) LO to RF RF to LO IQ Magnitude Imbalance IQ Phase Imbalance Noise Figure Noise Figure Under Blocking Conditions
RFIP, RFIN driven differentially through a balun -5 dBm each input tone -5 dBm each input tone RFIN, RFIP terminated in 50 LOIN, LOIP terminated in 50
With a -5 dBm input interferer 5 MHz away
Rev. 0 | Page 3 of 36
ADL5380
Parameter DYNAMIC PERFORMANCE at RF = 1900 MHz Conversion Gain Input P1dB RF Input Return Loss Second-Order Input Intercept (IIP2) Third-Order Input Intercept (IIP3) LO to RF RF to LO IQ Magnitude Imbalance IQ Phase Imbalance Noise Figure Noise Figure Under Blocking Conditions DYNAMIC PERFORMANCE at RF = 2700 MHz Conversion Gain Input P1dB RF Input Return Loss Second-Order Input Intercept (IIP2) Third-Order Input Intercept (IIP3) LO to RF RF to LO IQ Magnitude Imbalance IQ Phase Imbalance Noise Figure DYNAMIC PERFORMANCE at RF = 3600 MHz Conversion Gain Input P1dB RF Input Return Loss Second-Order Input Intercept (IIP2) Third-Order Input Intercept (IIP3) LO to RF RF to LO IQ Magnitude Imbalance IQ Phase Imbalance Noise Figure Noise Figure Under Blocking Conditions DYNAMIC PERFORMANCE at RF = 5800 MHz Conversion Gain Input P1dB RF Input Return Loss Second-Order Input Intercept (IIP2) Third-Order Input Intercept (IIP3) LO to RF RF to LO IQ Magnitude Imbalance IQ Phase Imbalance Noise Figure Noise Figure Under Blocking Conditions Condition VADJ ~ 4 V (set by 1.5 k from ADJ pin to VS) Min Typ 6.8 11.6 -13 61 27.8 -49 -77 0.07 0.25 11.7 14 7.4 11 -10 54 28 -49 -73 0.07 0.5 12.3 6.3 9.6 -11 48 21 -46 -72 0.14 1.1 14.2 16.2 5.8 8.2 -7.5 44 20.6 -47 -62 0.07 -1.25 15.5 18.9 Max Unit dB dBm dB dBm dBm dBm dBc dB Degrees dB dB dB dBm dB dBm dBm dBm dBc dB Degrees dB dB dBm dB dBm dBm dBm dBc dB Degrees dB dB dB dBm dB dBm dBm dBm dBc dB Degrees dB dB
RFIP, RFIN driven differentially through a balun -5 dBm each input tone -5 dBm each input tone RFIN, RFIP terminated in 50 LOIN, LOIP terminated in 50
With a -5 dBm input interferer 5 MHz away VADJ ~ 4 V (set by 1.5 k from ADJ pin to VS)
RFIP, RFIN driven differentially through a balun -5 dBm each input tone -5 dBm each input tone RFIN, RFIP terminated in 50 LOIN, LOIP terminated in 50
VADJ ~ 4.8 V (set by200 from ADJ pin to VS)
RFIP, RFIN driven differentially through a balun -5 dBm each input tone -5 dBm each input tone RFIN, RFIP terminated in 50 LOIN, LOIP terminated in 50
With a -5 dBm input interferer 5 MHz away VADJ ~ 2.4 V (ADJ pin left open)
RFIP, RFIN driven differentially through a balun -5 dBm each input tone -5 dBm each input tone RFIN, RFIP terminated in 50 LOIN, LOIP terminated in 50
With a -5 dBm input interferer 5 MHz away
Rev. 0 | Page 4 of 36
ADL5380 ABSOLUTE MAXIMUM RATINGS
Table 2.
Parameter Supply Voltage: VCC1, VCC2, VCC3 LO Input Power RF Input Power Internal Maximum Power Dissipation JA 1 Maximum Junction Temperature Operating Temperature Range Storage Temperature Range
1
Rating 5.5 V 13 dBm (re: 50 ) 15 dBm (re: 50 ) 1370 mW 53C/W 150C -40C to +85C -65C to +125C
Stresses above those listed under Absolute Maximum Ratings may cause permanent damage to the device. This is a stress rating only; functional operation of the device at these or any other conditions above those indicated in the operational section of this specification is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability.
ESD CAUTION
Per JDEC standard JESD 51-2. For information on optimizing thermal impedance, see the Thermal Grounding and Evaluation Board Layout section.
Rev. 0 | Page 5 of 36
ADL5380 PIN CONFIGURATION AND FUNCTION DESCRIPTIONS
24 23 22 21 20 19
GND3 GND1 IHI ILO GND1 VCC1 1 2 3 4 5 6
PIN 1 INDICATOR
VCC3 GND3 RFIP RFIN GND3 ADJ
18 17 16 15 14 13
ADL5380
TOP VIEW (Not to Scale)
GND3 GND2 QHI QLO GND2 VCC2
ENBL 7 GND4 8 LOIP 9 LOIN 10 GND4 11 NC 12
NOTES 1. NC = NO CONNECT. 2. THE EXPOSED PAD SHOULD BE CONNECTED TO A LOW IMPEDANCE THERMAL AND ELECTRICAL GROUND PLANE.
Figure 2. Pin Configuration
Table 3. Pin Function Descriptions
Pin No. 1, 2, 5, 8, 11, 14, 17, 18, 20, 23 3, 4, 15, 16 Mnemonic GND1, GND2, GND3, GND4 IHI, ILO, QLO, QHI Description Ground Connect. I Channel and Q Channel Mixer Baseband Outputs. These outputs have a 50 differential output impedance (25 per pin). Each output pair can swing 2 V p-p (differential) into a load of 200 . The output 3 dB bandwidth is ~400 MHz. Supply. Positive supply for LO, IF, biasing, and baseband sections. Decouple these pins to the board ground using the appropriate-sized capacitors. Enable Control. When pulled low, the part is fully enabled; when pulled high, the part is partially powered down and the output is disabled. Local Oscillator Input. Pins must be ac-coupled. A differential drive through a balun is necessary to achieve optimal performance. Recommended balun is the Mini-Circuits TC1-1-13 for lower frequencies, the Johanson Technology 3600 balun for midband frequencies, and the Johanson Technology 5400 balun for high band frequencies. Balun choice depends on the desired frequency range of operation. Do not connect this pin. A resistor to VS that optimizes third-order intercept. For operation <3 GHz, RADJ = 1.5 k. For operation from 3 GHz to 4 GHz, RADJ = 200 . For operation >5 GHz, RADJ = open. See the Circuit Description section for more details. RF Input. A single-ended 50 signal can be applied differentially to the RF inputs through a 1:1 balun. Recommended balun is the Mini-Circuits TC1-1-13 for lower frequencies, the Johanson Technology 3600 balun for midband frequencies, and the Johanson Technology 5400 balun for high band frequencies. Balun choice depends on the desired frequency range of operation. Exposed Paddle. Connect to a low impedance thermal and electrical ground plane.
6, 13, 24 7 9, 10
VCC1, VCC2, VCC3 ENBL LOIP, LOIN
12 19
NC ADJ
21, 22
RFIN, RFIP
EP
Rev. 0 | Page 6 of 36
07585-002
ADL5380 TYPICAL PERFORMANCE CHARACTERISTICS
VS = 5 V, TA = 25C, LO drive level = 0 dBm, RF input balun loss is de-embedded, unless otherwise noted.
LOW BAND OPERATION
RF = 400 MHz to 3 GHz; Mini-Circuits TC1-1-13 balun on LO and RF inputs, 1.5 k from the ADJ pin to VS.
18 16 14 12 10 8 6 -0.6 4 2 -0.8
07585-003
1.0 TA = -40C TA = +25C TA = +85C INPUT P1dB 0.8 0.6
GAIN (dB), IP1dB (dBm)
GAIN MISMATCH (dB)
0.4 0.2 0 -0.2 -0.4
GAIN
LO FREQUENCY (MHz)
LO FREQUENCY (MHz)
Figure 3. Conversion Gain and Input 1 dB Compression Point (IP1dB) vs. LO Frequency
80 70 60 I CHANNEL Q CHANNEL
2 1 0
Figure 5. IQ Gain Mismatch vs. LO Frequency
BASEBAND RESPONSE (dB)
IIP3, IIP2 (dBm)
INPUT IP2 50 40 30 20 10
-1 -2 -3 -4 -5 -6 -7
INPUT IP3 (I AND Q CHANNELS)
TA = -40C TA = +25C TA = +85C
07585-004
BASEBAND FREQUENCY (MHz)
LO FREQUENCY (MHz)
Figure 4. Input Third-Order Intercept (IIP3) and Input Second-Order Intercept Point (IIP2) vs. LO Frequency
Figure 6. Normalized IQ Baseband Frequency Response
Rev. 0 | Page 7 of 36
07585-006
-8
400
600
800
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2200
2000
2400
2600
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10
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-1.0
TA = -40C TA = +25C TA = +85C
400
600
800
400
600
800
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1400
1600
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2200
2400
2600
2800
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2600
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3000
ADL5380
18 17 16
NOISE FIGURE (dB)
35
IIP3 (dBm) AND NOISE FIGURE (dB)
TA = -40C TA = +25C TA = +85C
30 25 20 15 10 5 0
TA = -40C TA = +25C TA = +85C
300 280 260 240 SUPPLY CURRENT 220 200 NOISE FIGURE 180 160
INPUT IP3
15 14 13 12 11 10 9
07585-007
400
600
800
1000
1200
1400
1600
1800
2000
2200
2400
2600
2800
3000
1.0
1.5
2.0
2.5
3.0 VADJ (V)
3.5
4.0
4.5
LO FREQUENCY (MHz)
Figure 7. Noise Figure vs. LO Frequency
4 QUADRATURE PHASE ERROR (Degrees) 3 2 1 0 -1 -2 -3 -4 400 600 800 1000 1200 1400 1600 1800 2000 2200 2400 2600 2800 3000
07585-008
Figure 10. IIP3, Noise Figure, and Supply Current vs. VADJ, fLO = 900 MHz
25 23 21
NOISE FIGURE (dB)
19 17 15 13 11 920MHz 9 7
07585-011
1920MHz
TA = -40C TA = +25C TA = +85C
5 -30
-25
-20 -15 -10 -5 RF BLOCKER INPUT POWER (dBm)
0
5
LO FREQUENCY (MHz)
Figure 8. IQ Quadrature Phase Error vs. LO Frequency
20 75
Figure 11. Noise Figure vs. Input Blocker Level, fLO = 900 MHz, fLO = 1900 MHz (RF Blocker 5 MHz Offset)
18 60 IIP2, Q CHANNEL IIP2, I CHANNEL NOISE FIGURE 12 10 8 6 IIP3 4 2 -6 25 20 -5 -4 -3 -2 -1 0 1 2 LO LEVEL (dBm) 3 4 5 6 IP1dB GAIN 45 40 35 30 55 50
18 16 14 12 10 8 6 4 2 0 -6 -5
70 65 60
GAIN (dB), IP1dB (dBm), NOISE FIGURE (dB)
GAIN (dB), IP1dB (dBm), NOISE FIGURE (dB)
IIP2, I CHANNEL IIP2, Q CHANNEL
16 14
IIP3, IIP2 ( dBm)
IP1dB NOISE FIGURE GAIN
55 50 45 40 35
IIP3
30 -1 0 1 2 LO LEVEL (dBm) 3 4 5 6
07585-009
-4
-3
-2
Figure 9. Conversion Gain, IP1dB, Noise Figure, IIP3, and IIP2 vs. LO Level, fLO = 900 MHz
Figure 12. Conversion Gain, IP1dB, Noise Figure, IIP3, and IIP2 vs. LO Level, fLO = 2700 MHz
Rev. 0 | Page 8 of 36
07585-012
25
IIP3, IIP2 (dBm)
07585-010
8
SUPPLY CURRENT (mA)
ADL5380
35 30 25 INPUT IP3 20 15 10 NOISE FIGURE 5 0 1.0 1.5 2.0 2.5 3.0 VADJ (V) 3.5 4.0 4.5
-25 0.4 0.6 0.8 1.0 1.2 1.4 1.6 1.8 2.0 2.2 2.4 2.6 2.8 3.0 RF FREQUENCY (GHz) 0
IIP3 (dBm) AND NOISE FIGURE (dB)
TA = -40C TA = +25C TA = +85C
RETURN LOSS (dB)
07585-013
-5
-10
-15
-20
Figure 13. IIP3 and Noise Figure vs. VADJ, fLO = 2700 MHz
80 70
GAIN (dB), IP1dB (dBm), IIP2 I AND Q CHANNELS (dBm)
Figure 16. RF Port Return Loss vs. RF Frequency Measured on Characterization Board Through TC1-1-13 Balun
-20 -30 -40
60
LEAKAGE (dBm)
50 40 30 20 10
07585-014
-50 -60 -70 -80 -90 -100 0.4 0.6 0.8 1.0 1.2 1.4 1.6 1.8 2.0 2.2 2.4 2.6 2.8 3.0 LO FREQUENCY (GHz)
900MHz: GAIN 900MHz: IP1dB 900MHz: IIP2, I CHANNEL 900MHz: IIP2, Q CHANNEL 2700MHz: GAIN 2700MHz: IP1dB 2700MHz: IIP2, I CHANNEL 2700MHz: IIP2, Q CHANNEL
1
2
3 VADJ (V)
4
Figure 14. Conversion Gain, IP1dB, and IIP2 vs. VADJ, fLO = 900 MHz, fLO = 2700 MHz
40 35 30
IP1dB, IIP3 (dBm)
Figure 17. LO-to-RF Leakage vs. LO Frequency
90
-20 -30
80 IIP3 IIP2 75 70 65 60 IP1dB 55 50
IIP2, I AND Q CHANNELS (dBm)
TA = -40C TA = +25C TA = +85C
I CHANNEL Q CHANNEL
85
-40
LEAKAGE (dBc)
25 20 15 10 5 0
-50 -60 -70 -80 -90 -100 0.4 0.6 0.8 1.0 1.2 1.4 1.6 1.8 2.0 2.2 2.4 2.6 2.8 3.0 RF FREQUENCY (GHz)
Figure 15. IP1dB, IIP3, and IIP2 vs. Baseband Frequency
Figure 18. RF-to-LO Leakage vs. RF Frequency
Rev. 0 | Page 9 of 36
07585-018
4.5
6.5
8.5 10.5 12.5 14.5 16.5 BASEBAND FREQUENCY (MHz)
18.5
07585-015
07585-017
0
07585-016
ADL5380
0 -2 -4
RETURN LOSS (dB)
-6 -8 -10 -12 -14 -16 0.4 0.6 0.8 1.0 1.2 1.4 1.6 1.8 2.0 2.2 2.4 2.6 2.8 3.0 LO FREQUENCY (GHz)
Figure 19. LO Port Return Loss vs. LO Frequency Measured on Characterization Board Through TC1-1-13 Balun
07585-019
Rev. 0 | Page 10 of 36
ADL5380
MIDBAND OPERATION
RF = 3 GHz to 4 GHz; Johanson Technology 3600BL14M050T balun on LO and RF inputs, 200 from VADJ to VS.
14 13 12 TA = -40C TA = +25C TA = +85C IP1dB GAIN (dB), IP1dB (dBm), NOISE FIGURE (dB)
20 18 16 14 12 10 8 6 4 2 0 -6 -5 -4 -3 -2 -1 0 1 LO LEVEL (dBm) 2 3 4 5 6 IIP3 GAIN IIP2, I CHANNEL IIP2, Q CHANNEL
60 55 50 45 40 35 30 25 20 15
07585-023
07585-025
GAIN (dB), IP1dB (dBm)
11 10 9 8 7 6 5 3.0
IP1dB
GAIN
3.1
3.2
3.3 3.4 3.5 3.6 3.7 LO FREQUENCY (GHz)
3.8
3.9
4.0
Figure 20. Conversion Gain and Input 1 dB Compression Point (IP1dB) vs. LO Frequency
80 70 60 TA = -40C TA = +25C TA = +85C INPUT IP2
07585-020
4
10
Figure 23. Conversion Gain, IP1dB, Noise Figure, IIP3, and IIP2 vs. LO Level, fLO = 3600 MHz
18 17
I CHANNEL Q CHANNEL NOISE FIGURE (dB)
16 15 14 13 12 11 10 TA = -40C TA = +25C TA = +85C
IIP3, IIP2 (dBm)
50 40 30 20 INPUT IP3 I AND Q CHANNELS
9 3.0 3.1 3.2 3.3 3.4 3.5 3.6 3.7 LO FREQUENCY (GHz) 3.8 3.9 4.0
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3.0
3.1
3.2
3.3 3.4 3.5 3.6 3.7 LO FREQUENCY (GHz)
3.8
3.9
4.0
07585-021
10
8
Figure 21. Input Third-Order Intercept (IIP3) and Input Second-Order Intercept Point (IIP2) vs. LO Frequency
1.0
QUADRATURE PHASE ERROR (Degrees)
Figure 24. Noise Figure vs. LO Frequency
4
0.8 0.6
TA = -40C TA = +25C TA = +85C
3 2 1 0 -1 -2 -3 -4 3.0
TA = -40C TA = +25C TA = +85C
GAIN MISMATCH (dB)
0.4 0.2 0 -0.2 -0.4 -0.6 -0.8
07585-022
-1.0 3.0 3.2 3.4 3.6 LO FREQUENCY (GHz) 3.8 4.0
3.1
3.2
3.4 3.6 3.3 3.5 3.7 LO FREQUENCY (GHz)
3.8
3.9
4.0
Figure 22. IQ Gain Mismatch vs. LO Frequency
Figure 25. IQ Quadrature Phase Error vs. LO Frequency
Rev. 0 | Page 11 of 36
IIP3, IIP2 (dBm)
NOISE FIGURE
ADL5380
30 TA = -40C TA = +25C TA = +85C INPUT IP3 300
-20
IIP3 (dBm) AND NOISE FIGURE (dB)
25
280
-30
15
240
LEAKAGE (dBm)
CURRENT (mA)
20
260
-40
-50
10
NOISE FIGURE
220
-60
5 SUPPLY CURRENT
200
-70
07585-026
1.5
2.0
2.5
3.0 VADJ (V)
3.5
4.0
4.5
3.1
3.2
3.3
3.4 3.5 3.6 3.7 LO FREQUENCY (GHz)
3.8
3.9
4.0
Figure 26. IIP3, Noise Figure, and Supply Current vs. VADJ, fLO = 3600 MHz
25 23 21
Figure 29. LO-to-RF Leakage vs. LO Frequency
-20 -30 -40 LEAKAGE (dBc) -50 -60 -70 -80 -90
NOISE FIGURE (dB)
19 17 15 13 11 -30
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-25
-20
-15
-10
-5
0
5
3.1
3.2
3.3
RF POWEL LEVEL (dBm)
3.4 3.5 3.6 3.7 RF FREQUENCY (GHz)
3.8
3.9
4.0
Figure 27. Noise Figure vs. Input Blocker Level, fLO = 3600 MHz (RF Blocker 5 MHz Offset)
80 70 -2
GAIN (dB), IP1dB (dBm), IIP2 I AND Q CHANNELS (dBm)
Figure 30. RF-to-LO Leakage vs. RF Frequency
0
60
RETURN LOSS (dB)
50 40 30 20 10 0
07585-028
-4
3600MHz: GAIN 3600MHz: IP1dB 3600MHz: IIP2, I CHANNEL 3600MHz: IIP2, Q CHANNEL
-6
-8
-10
1
2
3
V ADJ (V)
4
3.1
3.2
3.3
3.4 3.5 3.6 3.7 RF FREQUENCY (GHz)
3.8
3.9
4.0
Figure 28. Conversion Gain, IP1dB, and IIP2 vs. VADJ, fLO = 3600 MHz
Figure 31. RF Port Return Loss vs. RF Frequency Measured on Characterization Board Through Johanson Technology 3600 Balun
Rev. 0 | Page 12 of 36
07585-031
-10
-12
07585-030
-100
07585-029
0 1.0
180
-80
ADL5380
0
-5
RETURN LOSS (dB)
-10
-15
-20
-25
3.1
3.2
3.3
3.4 3.5 3.6 3.7 LO FREQUENCY (GHz)
3.8
3.9
4.0
Figure 32. LO Port Return Loss vs. LO Frequency Measured on Characterization Board Through Johanson Technology 3600 Balun
07585-032
-30
Rev. 0 | Page 13 of 36
ADL5380
HIGH BAND OPERATION
RF = 5 GHz to 6 GHz; Johanson Technology 5400BL15B050E balun on LO and RF inputs, the ADJ pin is open.
12
GAIN (dB), IP1dB (dBm), NOISE FIGURE (dB)
20 18 16 14 12 10 8 6 4 2 0 -6 -5 -4 -3 -2 -1 0 1 LO LEVEL (dBm) 2 3 4 5 6 GAIN IIP2, I CHANNEL NOISE FIGURE IIP2, Q CHANNEL
60 55 50 45 40 35 30 25 20 15
07585-036
11
GAIN (dB), INPUT P1dB (dBm)
10 9 8 7 6 5 4 3 2 5.1 TA = -40C TA = +25C TA = +85C 5.2 5.3 5.4 5.5 5.6 5.7 LO FREQUENCY (GHz) 5.8 5.9 6.0
07585-033
INPUT P1dB
GAIN
IP1dB
IIP3
10
Figure 33. Conversion Gain and Input 1 dB Compression Point (IP1dB) vs. LO Frequency
80 70 60
IIP3, IIP2 (dBm)
Figure 36. Conversion Gain, IP1dB, Noise Figure, IIP3, and IIP2 vs. LO Level, fLO = 5800 MHz
20 TA = -40C TA = -25C TA = +85C
TA = -40C TA = +25C TA = +85C
I CHANNEL Q CHANNEL
19 18 17
NOISE FIGURE (dB)
INPUT IP2 50 40 30 20 10 5.1 INPUT IP3 (I AND Q CHANNELS)
16 15 14 13 12 11 10 9
07585-034
5.2
5.3
5.4 5.5 5.6 5.7 LO FREQUENCY (GHz)
5.8
5.9
6.0
5.0
5.1
5.2
5.3 5.4 5.5 5.6 5.7 LO FREQUENCY (GHz)
5.8
5.9
6.0
Figure 34. Input Third-Order Intercept (IIP3) and Input Second-Order Intercept Point (IIP2) vs. LO Frequency
1.0 0.8
IQ AMPLITUDE MISMATCH (dB)
Figure 37. Noise Figure vs. LO Frequency
4
IQ PHASE MISMATCH (Degrees)
0.6 0.4 0.2 0 -0.2 -0.4 -0.6 -0.8
TA = -40C TA = +25C TA = +85C
3 2 1 0 -1 -2 -3 -4
TA = -40C TA = +25C TA = +85C
07585-035
5.1
5.2
5.3
5.4 5.5 5.6 5.7 LO FREQUENCY (GHz)
5.8
5.9
6.0
5.1
5.2
5.3
5.4 5.5 5.6 5.7 LO FREQUENCY (GHz)
5.8
5.9
6.0
Figure 35. IQ Gain Mismatch vs. LO Frequency
Figure 38. IQ Quadrature Phase Error vs. LO Frequency
Rev. 0 | Page 14 of 36
07585-038
-1.0
07585-037
8
IIP3, IIP2 (dBm)
ADL5380
30 TA = -40C TA = +25C TA = +85C 300
-20 -30 -40
LEAKAGE (dBm)
IIP3 (dBm) AND NOISE FIGURE (dB)
25
INPUT IP3
280
NOISE FIGURE
CURRENT (mA)
20
260
-50 -60 -70 -80
15
240
10 SUPPLY CURRENT 5
220
200
-90 -10 0 5.1
07585-039
1.5
2.0
2.5
3.0 VADJ (V)
3.5
4.0
4.5
5.2
5.3
5.4 5.5 5.6 5.7 LO FREQUENC Y (GHz)
5.8
5.9
6.0
Figure 39. IIP3, Noise Figure, and Supply Current vs. VADJ, fLO = 5800 MHz
25
-20 -30
Figure 42. LO-to-RF Leakage vs. LO Frequency
20 NOISE FIGURE (dB)
-40
LEAKAGE (dBc)
15
-50 -60 -70 -80
10
5
-90
07585-040
-25
-20 -15 -10 RF POWER LEVEL (dBm)
-5
5.1
5.2
5.3
5.4 5.5 5.6 5.7 RF FREQUENCY (MHz)
5.8
5.9
6.0
Figure 40. Noise Figure vs. Input Blocker Level, fLO = 5800 MHz (RF Blocker 5 MHz Offset)
60
Figure 43. RF-to-LO Leakage vs. RF Frequency
0 -2 -4
RETURN LOSS (dB)
50
GAIN (dB), IP1dB (dBm), IIP2 I AND Q CHANNEL (dBm)
40 5800MHz: GAIN 5800MHz: IP1dB 5800MHz: IIP2, I CHANNEL 5800MHz: IIP2, Q CHANNEL
-6 -8 -10 -12
30
20
10
-14 -16 5.1 5.2 5.3 5.4 5.5 5.6 5.7 RF FREQUENCY (GHz) 5.8 5.9 6.0
1
2
3 VADJ (V)
4
Figure 41. Conversion Gain, IP1dB, and IIP2 vs. RBIAS, fLO = 5800 MHz
07585-041
Figure 44. RF Port Return Loss vs. RF Frequency Measured on Characterization Board Through Johanson Technology 5400 Balun
Rev. 0 | Page 15 of 36
07585-044
0
07585-043
0 -30
-100
07585-042
0 1.0
180
ADL5380
-0 -2 -4
RETURN LOSS (dB)
-6 -8 -10 -12 -14 -16 5.1 5.2 5.3 5.4 5.5 5.6 5.7 LO FREQUENCY (GHz) 5.8 5.9 6.0
Figure 45. LO Port Return Loss vs. LO Frequency Measured on Characterization Board Through Johanson Technology 5400 Balun
07585-045
Rev. 0 | Page 16 of 36
ADL5380
DISTRIBUTIONS FOR fLO = 900 MHz
100 90
DISTRIBUTION PERCENTAGE (%)
100 90
DISTRIBUTION PERCENTAGE (%)
80 70 60 50 40 30 20 10 0 28 29 30 31 32 INPUT IP3 (dBm) TA = -40C TA = +25C TA = +85C
80 70 60 50 40 30 20 10
TA = -40C TA = +25C TA = +85C I CHANNEL Q CHANNEL
33
34
07585-046
45
50
55
60 65 70 INPUT IP2 (dBm)
75
80
85
Figure 46. IIP3 Distributions
100 90
DISTRIBUTION PERCENTAGE (%)
IP1dB GAIN
Figure 49. IIP2 Distributions for I Channel and Q Channel
100 90
DISTRIBUTION PERCENTAGE (%)
80 70 60 50 40 30 20 10 0 4 5 6 7 8 9 10 11 GAIN (dB), IP1dB (dBm) 12 13 14 TA = -40C TA = +25C TA = +85C
07585-047
80 70 60 50 40 30 20 10 0 9.5 10.0 10.5 11.0 11.5 NOISE FIGURE (dB) TA = -40C TA = +25C TA = +85C 12.0 12.5
07585-050 07585-051
Figure 47. Gain and IP1dB Distributions
100 90
DISTRIBUTION PERCENTAGE (%)
100 90
Figure 50. Noise Figure Distributions
DISTRIBUTION PERCENTAGE (%)
80 70 60 50 40 30 20 10 0 -0.3 -0.2 TA = -40C TA = +25C TA = +85C
07585-048
80 70 60 50 40 30 20 10
TA = -40C TA = +25C TA = +85C
-0.1 0 0.1 GAIN MISMATCH (dB)
0.2
0.3
0 -1.0
-0.8
-0.6 -0.4 -0.2 0 0.2 0.4 0.6 QUADRATURE PHASE ERROR (Degrees)
0.8
1.0
Figure 48. IQ Gain Mismatch Distributions
Figure 51. IQ Quadrature Phase Error Distributions
Rev. 0 | Page 17 of 36
07585-049
0
ADL5380
DISTRIBUTIONS FOR fLO = 1900 MHz
100 90
100 90 DISTRIBUTION PERCENTAGE (%) 80 70 60 50 40 30 20 10
07585-052
DISTRIBUTION PERCENTAGE (%)
80 70 60 50 40 30 20 10 0 24 TA = -40C TA = +25C TA = +85C 25 26 27 28 29 INPUT IP3 (dBm) 30 31 32
TA = -40C TA = +25C TA = +85C I CHANNEL Q CHANNEL
45
50
55
60 65 INPUT IP2 (dBm)
70
75
80
Figure 52. IIP3 Distributions
100 90
DISTRIBUTION PERCENTAGE (%)
Figure 55. IIP2 Distributions for I Channel and Q Channel
100
80 70 60 50 40 30 20 10 4 5 6 7 8
DISTRIBUTION PERCENTAGE (%)
TA = -40C TA = +25C TA = +85C IP1dB GAIN
90 80 70 60 50 40 30 20 10 TA = -40C TA = +25C TA = +85C 11.0 11.5 12.0 12.5 13.0 13.5
07585-056 07585-057
9
10
11
12
13
14
GAIN (dB), IP1dB (dBm)
07585-053
0
0 10.5
NOISE FIGURE (dB)
Figure 53. Gain and IP1dB Distributions
100 90
DISTRIBUTION PERCENTAGE (%)
Figure 56. Noise Figure Distributions
100
DISTRIBUTION PERCENTAGE (%)
80 70 60 50 40 30 20 10
TA = -40C TA = +25C TA = +85C
90 80 70 60 50 40 30 20 10
07585-054
TA = -40C TA = +25C TA = +85C
0 -0.3
-0.2
-0.1 0 0.1 GAIN MISMATCH (dB)
0.2
0.3
0 -1.0
-0.8
-0.6 -0.4 -0.2 0 0.2 0.4 0.6 QUADRATURE PHASE ERROR (Degrees)
0.8
1.0
Figure 54. IQ Gain Mismatch Distributions
Figure 57. IQ Quadrature Phase Error Distributions
Rev. 0 | Page 18 of 36
07585-055
0
ADL5380
DISTRIBUTIONS FOR fLO = 2700 MHz
100 90
DISTRIBUTION PERCENTAGE (%)
100 90 DISTRIBUTION PERCENTAGE (%) 80 70 60 50 40 30 20 10
07585-058
80 70 60 50 40 30 20 10 0 18 20 22 24 26 28 30 INPUT IP3 (dBm) 32 34 36 TA = -40C TA = +25C TA = +85C
TA = -40C TA = +25C TA = +85C
I CHANNEL Q CHANNEL
35
40
45
50 55 60 INPUT IP2 (dBm)
65
70
75
Figure 58. IIP3 Distributions
100 90
DISTRIBUTION PERCENTAGE (%)
Figure 61. IIP2 Distributions for I Channel and Q Channel
100
80 70 60 50 40 30 20 10
DISTRIBUTION PERCENTAGE (%)
TA = -40C TA = +25C TA = +85C
IP1dB GAIN
90 80 70 60 50 40 30 20 10
07585-059
TA = -40C TA = +25C TA = +85C
4
5
6
7
8 9 10 11 GAIN (dB), IP1dB (dBm)
12
13
14
11.0
11.5
12.0 12.5 13.0 NOISE FIGURE (dB)
13.5
14.0
Figure 59. Gain and IP1dB Distributions
100 90
DISTRIBUTION PERCENTAGE (%)
100 90
Figure 62. Noise Figure Distributions
80 70 60 50 40 30 20 10 0 -0.3 TA = -40C TA = +25C TA = +85C
07585-060
DISTRIBUTION PERCENTAGE (%)
80 70 60 50 40 30 20 10
TA = -40C TA = +25C TA = +85C
-0.2
-0.1 0 0.1 GAIN MISMATCH (dB)
0.2
0.3
-1.5
-1.0 -0.5 0 0.5 1.0 QUADRATURE PHASE ERROR (Degrees)
1.5
2.0
Figure 60. IQ Gain Mismatch Distributions
Figure 63. IQ Quadrature Phase Error Distributions
Rev. 0 | Page 19 of 36
07585-063
0 -2.0
07585-062
0
0 10.5
07585-061
0
ADL5380
DISTRIBUTIONS FOR fLO = 3600 MHz
100 90 100 90 TA = -40C TA = +25C TA = +85C I CHANNEL Q CHANNEL
DISTRIBUTION PERCENTAGE (%)
80 70 60 50 40 30 20 10 15 17 19 21 23 25 27 INPUT IP3 (dBm) 29 31 33
07585-064
DISTRIBUTION PERCENTAGE (%)
80 70 60 50 40 30 20 10
TA = -40C TA = +25C TA = +85C
35
40
45
50 55 INPUT IP2 (dBm)
60
65
70
Figure 64. IIP3 Distributions
100 90 IP1dB GAIN 100 90
Figure 67. IIP2 Distributions for I Channel and Q Channel
DISTRIBUTION PERCENTAGE (%)
80 70 60 50 40 30 20 10
07585-065
DISTRIBUTION PERCENTAGE (%)
80 70 60 50 40 30 20 10
TA = -40C TA = +25C TA = +85C
TA = -40C TA = +25C TA = +85C
0 4 5 6 7 8 9 10 11 GAIN (dB), IP1dB (dBm) 12 13 14
13.0
13.5
14.0 14.5 15.0 NOISE FIGURE (dB)
15.5
16.0
Figure 65. Gain and IP1dB Distributions
100 90 DISTRIBUTION PERCENTAGE (%)
DISTRIBUTION PERCENTAGE (%)
Figure 68. Noise Figure Distributions
100
80 70 60 50 40 30 20 10
TA = -40C TA = +25C TA = +85C
90 80 70 60 50 40 30 20 10
07585-066
TA = -40C TA = +25C TA = +85C
-0.2
-0.1 0 0.1 GAIN MISMATCH (dB)
0.2
0.3
0 0.5 1.0 1.5 2.0 QUADRATURE PHASE ERROR (Degrees)
2.5
Figure 66. IQ Gain Mismatch Distributions
Figure 69. IQ Quadrature Phase Error Distributions
Rev. 0 | Page 20 of 36
07585-069
0 -0.3
0 -0.5
07585-068
0 12.5
07585-067
0
0
ADL5380
DISTRIBUTIONS FOR fLO = 5800 MHz
100 90
DISTRIBUTION PERCENTAGE (%)
100 TA = -40C TA = +25C TA = +85C 90 TA = -40C TA = +25C TA = +85C I CHANNEL Q CHANNEL
80 70 60 50 40 30 20 10
DISTRIBUTION PERCENTAGE (%)
07585-070
80 70 60 50 40 30 20 10
19
20
21 22 INPUT IP3 (dBm)
23
24
30
35
40
45 50 55 INPUT IP2 (dBm)
60
65
70
Figure 70. IIP3 Distributions
100 90
DISTRIBUTION PERCENTAGE (%)
Figure 73. IIP2 Distributions for I Channel and Q Channel
100
80 70 60 50 40 30 20 10 2
DISTRIBUTION PERCENTAGE (%)
TA = -40C TA = +25C TA = +85C IP1dB GAIN
90 80 70 60 50 40 30 20 10
TA = -40C TA = +25C TA = +85C
13.5
14.0
14.5
15.0
15.5
16.0
16.5
17.0
17.5
18.0
NOISE FIGURE (dB)
Figure 71. Gain and IP1dB Distributions
100 90 TA = -40C TA = +25C TA = +85C
Figure 74. Noise Figure Distributions
100 90 TA = -40C TA = +25C TA = +85C
DISTRIBUTION PERCENTAGE (%)
DISTRIBUTION PERCENTAGE (%)
80 70 60 50 40 30 20 10
80 70 60 50 40 30 20 10
07585-072
-0.2
-0.1 0 0.1 GAIN MISMATCH (dB)
0.2
0.3
-2 -1 0 1 2 QUADRATURE PHASE ERROR (Degrees)
3
Figure 72. IQ Gain Mismatch Distributions
Figure 75. IQ Quadrature Phase Error Distributions
Rev. 0 | Page 21 of 36
07585-075
0 -0.3
0 -3
07585-074
3
4
5 6 7 GAIN (dB), IP1dB (dBm)
8
9
10
07585-071
0
0 13.0
07585-073
0 18
0
ADL5380 CIRCUIT DESCRIPTION
The ADL5380 can be divided into five sections: the local oscillator (LO) interface, the RF voltage-to-current (V-to-I) converter, the mixers, the differential emitter follower outputs, and the bias circuit. A detailed block diagram of the device is shown in Figure 76.
ENBL ADJ
Table 4. ADJ Pin Resistor Values and Approximate ADJ Pin Voltages
RADJ 200 to VS 600 to VS 1.54 k to VS 3.8 k to VS 10 k to VS Open 9 k to GND 3.5 k to GND 1.5 k to GND ~VADJ (V) 4.8 4.5 4 3.5 3 2.5 2 1.5 1 ~ Baseband CommonMode Output (V) 2.2 2.3 2.5 2.7 3 3.2 3.4 3.6 3.8
ADL5380
BIAS
IHI
ILO
LOIP RFIN V2I RFIP QUADRATURE PHASE SPLITTER LOIN QHI
MIXERS
The ADL5380 has two double-balanced mixers: one for the inphase channel (I channel) and one for the quadrature channel (Q channel). These mixers are based on the Gilbert cell design of four cross-connected transistors. The output currents from the two mixers are summed together in the resistive loads that then feed into the subsequent emitter follower buffers.
Figure 76. Block Diagram
07585-076
QLO
The LO interface generates two LO signals at 90 of phase difference to drive two mixers in quadrature. RF signals are converted into currents by the V-to-I converters that feed into the two mixers. The differential I and Q outputs of the mixers are buffered via emitter followers. Reference currents to each section are generated by the bias circuit. A detailed description of each section follows.
EMITTER FOLLOWER BUFFERS
The output emitter followers drive the differential I and Q signals off chip. The output impedance is set by on-chip 25 series resistors that yield a 50 differential output impedance for each baseband port. The fixed output impedance forms a voltage divider with the load impedance that reduces the effective gain. For example, a 500 differential load has 1 dB lower effective gain than a high (10 k) differential load impedance.
LO INTERFACE
The LO interface consists of a polyphase quadrature splitter followed by a limiting amplifier. The LO input impedance is set by the polyphase, which splits the LO signal into two differential signals in quadrature. The LO input impedance is nominally 50 . Each quadrature LO signal then passes through a limiting amplifier that provides the mixer with a limited drive signal. For optimal performance, the LO inputs must be driven differentially.
BIAS CIRCUIT
A band gap reference circuit generates the reference currents used by different sections. The bias circuit can be enabled and partially disabled using ENBL (Pin 7). If ENBL is grounded or left open, the part is fully enabled. Pulling ENBL high shuts off certain sections of the bias circuitry, reducing the standing power to about half of its fully enabled consumption and disabling the outputs.
V-TO-I CONVERTER
The differential RF input signal is applied to a V-to-I converter that converts the differential input voltage to output currents. The V-to-I converter provides a differential 50 input impedance. The V-to-I bias current can be adjusted up or down using the ADJ pin (Pin 19). Adjusting the current up improves IIP3 and IP1dB but degrades SSB NF. Adjusting the current down improves SSB NF but degrades IIP3 and IP1dB. The current adjustment can be made by connecting a resistor from the ADJ pin (Pin 19) to VS to increase the bias current or to ground to decrease the bias current. Table 4 approximately dictates the relationship between the resistor used (RADJ), the resulting ADJ pin voltage, and the resulting baseband common-mode output voltage.
Rev. 0 | Page 22 of 36
ADL5380 APPLICATIONS INFORMATION
BASIC CONNECTIONS
Figure 78 shows the basic connections schematic for the ADL5380.
LOCAL OSCILLATOR (LO) INPUT
For optimum performance, drive the LO port differentially through a balun. The recommended balun for each performance level includes the following: * Up to 3 GHz is the Mini-Circuits TC1-1-13. * From 3 GHz to 4 GHz is the Johanson Technology 3600BL14M050. * From 4.9 GHz to 6 GHz is the Johanson Technology 5400BL15B050. AC couple the LO inputs to the device with 100 pF capacitors. The LO port is designed for a broadband 50 match from 400 MHz to 6 GHz. The LO return loss can be seen in Figure 19. Figure 77 shows the LO input configuration.
LO INPUT
9
POWER SUPPLY
The nominal voltage supply for the ADL5380 is 5 V and is applied to the VCC1, VCC2, and VCC3 pins. Connect ground to the GND1, GND2, GND3, and GND4 pins. Solder the exposed paddle on the underside of the package to a low thermal and electrical impedance ground plane. If the ground plane spans multiple layers on the circuit board, these layers should be stitched together with nine vias under the exposed paddle. The AN-772 Application Note discusses the thermal and electrical grounding of the LFCSP in detail. Decouple each of the supply pins using two capacitors; recommended capacitor values are 100 pF and 0.1 F.
LOIP
BALUN
100pF
10
LOIN
07585-077
100pF
Figure 77. Differential LO Drive
The recommended LO drive level is between -6 dBm and +6 dBm. The applied LO frequency range is between 400 MHz and 6 GHz.
RFIN BALUN
100pF
100pF
VS 0.1F 100pF 24 23 22 21 20 19
RADJ VS
GND3
RFIN
RFIP
GND3
VCC3
1
GND3
GND3 18 GND2 17 QHI 16 QHI QLO
2 GND1
IHI
3 IHI ILO 4 ILO 5 GND1
ADL5380
GND2 14
GND4
GND4
ENBL
LOIN
LOIP
VS 0.1F 100pF
6 VCC1
VCC2 13
ADJ
QLO 15
VS 100pF 0.1F
7
8
9
10
11
100pF BALUN
100pF
NC
12
LO_SE
Figure 78. Basic Connections Schematic
Rev. 0 | Page 23 of 36
07585-078
ADL5380
RF INPUT
The RF inputs have a differential input impedance of approximately 50 . For optimum performance, drive the RF port differentially through a balun. The recommended balun for each performance level includes the following: * * * Up to 3 GHz is the Mini-Circuits TC1-1-13. From 3 GHz to 4 GHz is the Johanson Technology 3600BL14M050. From 4.9 GHz to 6 GHz is the Johanson Technology 5400BL15B050.
IHI
3 16
QHI
ADL5380
07585-081 07585-082
ILO
4
15
QLO
Figure 81. Baseband Output Configuration
ERROR VECTOR MAGNITUDE (EVM) PERFORMANCE
EVM is a measure used to quantify the performance of a digital radio transmitter or receiver. A signal received by a receiver has all constellation points at their ideal locations; however, various imperfections in the implementation (such as magnitude imbalance, noise floor, and phase imbalance) cause the actual constellation points to deviate from their ideal locations. In general, a demodulator exhibits three distinct EVM limitations vs. received input signal power. At strong signal levels, the distortion components falling in-band due to nonlinearities in the device cause strong degradation to EVM as signal levels increase. At medium signal levels, where the demodulator behaves in a linear manner and the signal is well above any notable noise contributions, the EVM has a tendency to reach an optimum level determined dominantly by the quadrature accuracy of the demodulator and the precision of the test equipment. As signal levels decrease, such that noise is a major contribution, the EVM performance vs. the signal level exhibits a decibel-fordecibel degradation with decreasing signal level. At lower signal levels, where noise proves to be the dominant limitation, the decibel EVM proves to be directly proportional to the SNR. The ADL5380 shows excellent EVM performance for various modulation schemes. Figure 82 shows the EVM performance of the ADL5380 with a 16 QAM, 200 kHz low IF.
0 -5 -10 -15
AC couple the RF inputs to the device with 100 pF capacitors. Figure 79 shows the RF input configuration.
21
RFIN
100pF BALUN 100pF
22
RFIP
RF INPUT
07585-079
Figure 79. RF Input
The differential RF port return loss is characterized, as shown in Figure 80.
-8
DIFFERENTIAL RETURN LOSS RF PORT (dB)
-10 -12 -14 -16 -18 -20 -22 -24
EVM (dB)
0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 RF FREQUENCY (GHz) 4.5 5.0 5.5 6.0
07585-080
-26 -28 -30
-20 -25 -30 -35 -40 -45 -50 -90 -70 -50 -30 RF INPUT POWER (dBm) -10 10
Figure 80. Differential RF Port Return Loss
BASEBAND OUTPUTS
The baseband outputs QHI, QLO, IHI, and ILO are fixed impedance ports. Each baseband pair has a 50 differential output impedance. The outputs can be presented with differential loads as low as 200 (with some degradation in gain) or high impedance differential loads (500 or greater impedance yields the same excellent linearity) that is typical of an ADC. The TCM9-1 9:1 balun converts the differential IF output to a single-ended output. When loaded with 50 , this balun presents a 450 load to the device. The typical maximum linear voltage swing for these outputs is 2 V p-p differential. The output 3 dB bandwidth is 390 MHz. Figure 81 shows the baseband output configuration.
Rev. 0 | Page 24 of 36
Figure 82. EVM, RF = 900 MHz, IF = 200 kHz vs. RF Input Power for a 16 QAM 160ksym/s Signal
ADL5380
Figure 83 shows the zero-IF EVM performance of a 10 MHz IEEE 802.16e WiMAX signal through the ADL5380. The differential dc offsets on the ADL5380 are in the order of a few millivolts. However, ac coupling the baseband outputs with 10 F capacitors eliminates dc offsets and enhances EVM performance. With a 10 MHz BW signal, 10 F ac coupling capacitors with the 500 differential load results in a high-pass corner frequency of ~64 Hz, which absorbs an insignificant amount of modulated signal energy from the baseband signal. By using ac coupling capacitors at the baseband outputs, the dc offset effects, which can limit dynamic range at low input power levels, can be eliminated.
0
Figure 84 exhibits multiple W-CDMA low-IF EVM performance curves over a wide RF input power range into the ADL5380. In the case of zero-IF, the noise contribution by the vector signal analyzer becomes predominant at lower power levels, making it difficult to measure SNR accurately.
-10 -15 -20
EVM (dB)
-25 -30 0Hz IF -35 2.5MHz LOW-IF -40 5MHz LOW-IF
-10
-20
EVM (dB)
-30 5.8GHz 3.5GHz -50 2.6GHz -65 -55 -45 -35 -25 -15 -5 5
07585-083
-70
-60
-50 -40 -30 -20 RF INPUT POWER (dBm)
-10
0
10
-40
Figure 84. EVM, RF = 1900 MHz, IF = 0 Hz, IF = 2.5 MHz, IF = 5 MHz, and IF = 7.5 MHz vs. RF Input Power for a W-CDMA Signal (AC-Coupled Baseband Outputs)
LOW IF IMAGE REJECTION
The image rejection ratio is the ratio of the intermediate frequency (IF) signal level produced by the desired input frequency to that produced by the image frequency. The image rejection ratio is expressed in decibels. Appropriate image rejection is critical because the image power can be much higher than that of the desired signal, thereby plaguing the down-conversion process. Figure 85 illustrates the image problem. If the upper sideband (lower sideband) is the desired band, a 90 shift to the Q channel (I channel) cancels the image at the lower sideband (upper sideband). Phase and gain balance between I and Q channels are critical for high levels of image rejection.
-60 -75
RF INPUT POWER (dBm)
Figure 83. EVM, RF = 2.6 GHz, RF = 3.5 GHz, and RF = 5.8 GHz, IF = 0 Hz vs. RF Input Power for a 16 QAM 10 MHz Bandwidth Mobile WiMAX Signal (AC-Coupled Baseband Outputs)
COSLOt
0
IF
IF
-IF 0 +IF -90 0 +IF
+90
LSB
LO
USB
-IF SINLOt 0 +IF
0
0
+IF
07585-085
Figure 85. Illustration of the Image Problem
Rev. 0 | Page 25 of 36
07585-084
-45 -80
7.5MHz LOW-IF
ADL5380
Figure 86 and Figure 87 show the excellent image rejection capabilities of the ADL5380 for low IF applications, such as W-CDMA. The ADL5380 exhibits image rejection greater than 45 dB over a broad frequency range.
60
50
IMAGE REJECTION (dB)
40
2.5MHz LOW IF 5MHz LOW IF 7MHz LOW IF
It is necessary to consider the overall source and load impedance presented by the ADL5380 and ADC input when designing the filter network. The differential baseband output impedance of the ADL5380 is 50 . The ADL5380 is designed to drive a high impedance ADC input. It may be desirable to terminate the ADC input down to lower impedance by using a terminating resistor, such as 500 . The terminating resistor helps to better define the input impedance at the ADC input at the cost of a slightly reduced gain (see the Circuit Description section for details on the emitter-follower output loading effects). The order and type of filter network depends on the desired high frequency rejection required, pass-band ripple, and group delay. Filter design tables provide outlines for various filter types and orders, illustrating the normalized inductor and capacitor values for a 1 Hz cutoff frequency and 1 load. After scaling the normalized prototype element values by the actual desired cut-off frequency and load impedance, the series reactance elements are halved to realize the final balanced filter network component values. As an example, a second-order Butterworth, low-pass filter design is shown in Figure 88 where the differential load impedance is 500 and the source impedance of the ADL5380 is 50 . The normalized series inductor value for the 10-to-1, load-to-source impedance ratio is 0.074 H, and the normalized shunt capacitor is 14.814 F. For a 10.9 MHz cutoff frequency, the single-ended equivalent circuit consists of a 0.54 H series inductor followed by a 433 pF shunt capacitor. The balanced configuration is realized as the 0.54 H inductor is split in half to realize the network shown in Figure 88.
30
20
10
07585-103
0 400
800
1200
1600 2000 2400 2800 RF FREQUENCY (MHz)
3200 3600
4000
Figure 86. Low Band and Midband Image Rejection vs. RF Frequency for a W-CDMA Signal, IF = 2.5 MHz, 5 MHz, and 7.5 MHz
60
50
IMAGE REJECTION (dB)
40 2.5MHz LOW IF 5MHz LOW IF 7MHz LOW IF
30
20
10
07585-104
RS = 50
LN = 0.074H NORMALIZED SINGLE-ENDED CONFIGURATION
0 5000
5200
5400 5600 RF FREQUENCY (MHz)
5800
6000
VS
CN
14.814F
RL= 500
Figure 87. High Band Image Rejection vs. RF Frequency for a W-CDMA Signal, IF = 2.5 MHz, 5 MHz, and 7.5 MHz
RS = 0.1 RL RS = 50 VS 0.54H DENORMALIZED SINGLE-ENDED EQUIVALENT
fC = 1Hz
EXAMPLE BASEBAND INTERFACE
In most direct-conversion receiver designs, it is desirable to select a wanted carrier within a specified band. The desired channel can be demodulated by tuning the LO to the appropriate carrier frequency. If the desired RF band contains multiple carriers of interest, the adjacent carriers are also down converted to a lower IF frequency. These adjacent carriers can be problematic if they are large relative to the wanted carrier because they can overdrive the baseband signal detection circuitry. As a result, it is often necessary to insert a filter to provide sufficient rejection of the adjacent carriers.
433pF
RL= 500
RS = 25 2 VS
fC = 10.9MHz
0.27H BALANCED CONFIGURATION RL 2 = 250 RL = 250 2
433pF
RS = 25 2
0.27H
Figure 88. Second-Order Butterworth, Low-Pass Filter Design Example
Rev. 0 | Page 26 of 36
07585-087
ADL5380
A complete design example is shown in Figure 91. A sixth-order Butterworth differential filter having a 1.9 MHz corner frequency interfaces the output of the ADL5380 to that of an ADC input. The 500 load resistor defines the input impedance of the ADC. The filter adheres to typical direct conversion W-CDMA applications where, 1.92 MHz away from the carrier IF frequency, 1 dB of rejection is desired, and, 2.7 MHz away from the carrier IF frequency, 10 dB of rejection is desired. Figure 89 and Figure 90 show the measured frequency response and group delay of the filter.
10 900 800 700 600 500 400 300 200 100 5
DELAY (ns)
0
0.2
0.4
0.6
0.8
1.0
1.2
1.4
1.6
1.8
MAGNITUDE RESPONSE (dB)
FREQUENCY (MHz)
0
Figure 90. Sixth-Order Baseband Filter Group Delay
-5
-10
-15
0
0.5
1.0
1.5
2.0
2.5
3.0
3.5
FREQUENCY (MHz)
Figure 89. Sixth-Order Baseband Filter Response
07585-088
-20
Rev. 0 | Page 27 of 36
07585-089
ADL5380
RFIN BALUN
100pF
100pF
VS 0.1F 100pF 24 23 22 21 20 19 GND3 18 GND2 17 QHI 16
VS
RFIP
GND3
RFIN
GND3
VCC3
1 GND3 2 GND1 3 IHI 4 ILO 5 GND1
ADL5380
GND2 14
GND4
100pF
NC
0.1F
GND4
ENBL
LOIN
LOIP
VS
ADJ
QLO 15
6 VCC1
VCC2 13 100pF 12
VS 0.1F
7
8
9
10
11
100pF BALUN
100pF
LO_SE
CAC 10F 27H
CAC 10F 27H
CAC 10F 27H
CAC 10F 27H
270pF
270pF
27H
100pF
27H
27H
100pF
27H
10H
68pF
10H
10H
68pF
10H
500 ADC INPUT
500 ADC INPUT
07585-090
Figure 91. Sixth-Order Low-Pass Butterworth, Baseband Filter Schematic
Rev. 0 | Page 28 of 36
ADL5380
As the load impedance of the filter increases, the filter design becomes more challenging in terms of meeting the required rejection and pass band specifications. In the previous W-CDMA example, the 500 load impedance resulted in the design of a sixth-order filter that has relatively large inductor values and small capacitor values. If the load impedance is 200 , the filter design becomes much more manageable. Figure 92 shows a fourth-order filter designed for a 10 MHz wide LTE signal. As shown in Figure 92, the resultant inductor and capacitor values become much more practical with a 200 load.
2.2H 1.5H
Figure 93 and Figure 94 illustrate the magnitude response and group delay response of the fourth-order filter, respectively.
5 0
FREQUENCY RESPONSE (dB)
-5 -10 -15 -20 -25 -30 -35 0 5 10 15 20 25 30 35 40
07585-092
100pF
22pF
200
50
-40
07585-091
2.2H
1.5H
FREQUENCY (MHz)
Figure 92. Fourth-Order Low-Pass LTE Filter Schematic
Figure 93. Fourth-Order Low-Pass LTE Filter Magnitude Response
60
50
GROUP DELAY (ns)
40
30
20
10
0
5
10
15
20
25
30
35
40
FREQUENCY (MHz)
Figure 94. Fourth-Order Low-Pass LTE Filter Group Delay Response
Rev. 0 | Page 29 of 36
07585-093
0
ADL5380 CHARACTERIZATION SETUPS
Figure 95 to Figure 97 show the general characterization bench setups used extensively for the ADL5380. The setup shown in Figure 97 was used to do the bulk of the testing and used sinusoidal signals on both the LO and RF inputs. An automated Agilent VEE program was used to control the equipment over the IEEE bus. This setup was used to measure gain, IP1dB, IIP2, IIP3, I/Q gain match, and quadrature error. The ADL5380 characterization board had a 9-to-1 impedance transformer on each of the differential baseband ports to do the differential-tosingle-ended conversion, which presented a 450 differential load to each baseband port, when interfaced with 50 test equipment. For all measurements of the ADL5380, the loss of the RF input balun was de-embedded. Due to the wideband nature of the ADL5380, three different board configurations had to be used to characterize the product. For low band characterization (400 MHz to 3 GHz), the Mini-Circuits TC1-1-13 balun was used on the RF and LO inputs to create differential signals at the device pins. For midband characterization (3 GHz to 4 GHz), the Johanson Technology 3600BL14M050T was used, and for high band characterization (5 GHz to 6 GHz), the Johanson Technology 5400BL15B050E balun was used. The two setups shown in Figure 95 and Figure 96 were used for making NF measurements. Figure 95 shows the setup for measuring NF with no blocker signal applied while Figure 96 was used to measure NF in the presence of a blocker. For both setups, the noise was measured at a baseband frequency of 10 MHz. For the case where a blocker was applied, the output blocker was at a 15 MHz baseband frequency. Note that great care must be taken when measuring NF in the presence of a blocker. The RF blocker generator must be filtered to prevent its noise (which increases with increasing generator output power) from swamping the noise contribution of the ADL5380. At least 30 dB of attention at the RF and image frequencies is desired. For example, assume a 915 MHz signal applied to the LO inputs of the ADL5380. To obtain a 15 MHz output blocker signal, the RF blocker generator is set to 930 MHz and the filters tuned such that there is at least 30 dB of attenuation from the generator at both the desired RF frequency (925 MHz) and the image RF frequency (905 MHz). Finally, the blocker must be removed from the output (by the 10 MHz low-pass filter) to prevent the blocker from swamping the analyzer.
SNS CONTROL
FROM SNS PORT
OUTPUT
AGILENT N8974A NOISE FIGURE ANALYZER
RF GND VPOS CHAR BOARD HP 6235A POWER SUPPLY LO
6dB PAD
ADL5380
Q I
R1 50
INPUT
IEEE
LOW-PASS FILTER
AGILENT 8665B SIGNAL GENERATOR IEEE
PC CONTROLLER
Figure 95. General Noise Figure Measurement Setup
Rev. 0 | Page 30 of 36
07585-095
ADL5380
BAND-PASS TUNABLE FILTER R&S SMT03 SIGNAL GENERATOR
BAND-REJECT TUNABLE FILTER
6dB PAD
RF GND VPOS CHAR BOARD HP 6235A POWER SUPPLY LO
Q
R1 50 LOW-PASS FILTER
R&S FSEA30 SPECTRUM ANALYZER
ADL5380
6dB PAD I
6dB PAD
BAND-PASS CAVITY FILTER
HP 87405 LOW NOISE PREAMP
07585-096
AGILENT 8665B SIGNAL GENERATOR
Figure 96. Measurement Setup for Noise Figure in the Presence of a Blocker
3dB PAD RF AMPLIFIER RF IEEE 3dB PAD IN VP GND 3dB PAD R&S SMT06 AGILENT 11636A OUT 3dB PAD
RF IEEE 6dB PAD RF IEEE GND VPOS CHAR BOARD AGILENT E3631 POWER SUPPLY LO 6dB PAD I 6dB PAD
R&S SMT06
Q 6dB PAD SWITCH MATRIX
ADL5380
IEEE
AGILENT E8257D SIGNAL GENERATOR
IEEE
IEEE
IEEE
07585-097
RF INPUT
PC CONTROLLER
R&S FSEA30 SPECTRUM ANALYZER
HP 8508A VECTOR VOLTMETER
Figure 97. General Characterization Setup
Rev. 0 | Page 31 of 36
INPUT CHANNELS A AND B
ADL5380 EVALUATION BOARD
The ADL5380 evaluation board is available. There are two versions of the board, optimized for performance for separate frequency ranges. For operation <3 GHz, an FR4 material-based board with the TC1-1-13 balun footprint is available. For operation between 3 GHz to 6 GHz, a Rogers(R) material-based RO3003 board with the Johanson Technology 3600BL14M050 balun (optimal for operation between 3 GHz and 4 GHz) footprint is available. The Johanson Technology 5400BL15K050 shares the same footprint and can be used for operation between 4900 MHz to 5800 MHz. The board can be used for single-ended or differential baseband analysis. The default configuration of the board is for single-ended baseband analysis.
RFx
T3x
C5x R19x VPOS C11x C8x
24 23 22
C12x R23x
21 20 19
VPOS
RFIP
GND3
RFIN
GND3
VCC3
ADJ
1
GND3 GND1 IHI ILO GND1 VCC1
GND4 GND4 ENBL LOIN LOIP NC
GND3 18 GND2 17 QHI R14x
16
IPx R17x T4x
R5x R16x
2 3
R3x R18x T2x
QPx
C16x R15x
R7x
ADL5380
R6x QLO 15 GND2 14 VCC2 13 C7x R12x
4 5
C15x R13x
INx
R4x VPOS C9x
QNx R2x VPOS C10x
R10x
6
C6x
7
8
9
10
11
12
R9x R11x VPOS
R1x C2x C1x C3x C4x T1x LOPx LO_SE LONx
P1x VPOS
NOTES 1. X = B, FOR LOW FREQUENCY OPERATION UP TO 3GHz, TC1-1-13 BALUN ON RF AND LO PORTS. X = A, FOR FREQUENCY OPERATION FROM 3GHz TO 4GHz, JOHANSON TECHNOLOGY 3600BL14M050 BALUN ON RF AND LO PORTS. 2. FOR OPERATION BETWEEN 4.9GHZ TO 6GHZ, THE JOHANSON TECHNOLOGY 5400BL15K050 BALUN, WHICH SHARES A SIMILAR FOOTPRINT AS THE 4GHZ BALUN, CAN BE USED.
07585-098
Figure 98. Evaluation Board Schematic
Rev. 0 | Page 32 of 36
ADL5380
Table 5. Evaluation Board Configuration Options
Component VPOSx, GNDx R10x, R12x, R19x C6x to C11x P1x, R11x, R9x, R1x R23x C1x to C5x, C12x R2x to R7x, R13x to R18x Description Power Supply and Ground Vector Pins. Power Supply Decoupling. Shorts or power supply decoupling resistors. The capacitors provide the required dc coupling up to 6 GHz. Device Enable. When connected to VS, the device is active. Adjust Pin. The resistor value here sets the bias voltage at this pin and optimizes third-order distortion. AC Coupling Capacitors. These capacitors provide the required ac coupling from 400 MHz to 4 GHz. Single-Ended Baseband Output Path. This is the default configuration of the evaluation board. R13x to R18x are populated for appropriate balun interface. R2x to R5x are not populated. Baseband outputs are taken from QHI and IHI. The user can reconfigure the board to use full differential baseband outputs. R2x to R5x provide a means to bypass the 9:1 TCM9-1 transformer to allow for differential baseband outputs. Access the differential baseband signals by populating R2x to R5x with 0 and not populating R13x to R18x. This way the transformer does not need to be removed. The baseband outputs are taken from the SMAs of QHI, QLO, IHI, and ILO. R6x and R7x are provisions for applying a specific differential load across the baseband outputs IF Output Interface. TCM9-1 converts a differential high impedance IF output to a single-ended output. When loaded with 50 , this balun presents a 450 load to the device. The center tap can be decoupled through a capacitor to ground. Decoupling Capacitors. C15x and C16x are the decoupling capacitors used to reject noise on the center tap of the TCM9-1. LO Input Interface. A 1:1 RF balun that converts the single-ended RF input to differential signal is used. Default Condition Not applicable R10x, R12x, R19x = 0 (0603) C6x, C7x, C8x = 100 pF (0402), C9x, C10x, C11x = 0.1 F (0603) P1x, R9x = DNI, R1x = DNI, R11x = 0 R23B = 1.5 k (0603), R23A = 200 (0603) C1x, C4x = DNI, C2x, C3x, C5x, C12x = 100 pF (0402) R2x to R7x = open, R13x to R18x = 0 (0402)
T2x, T4x
T2x, T4x = TCM9-1, 9:1 (Mini-Circuits)
C15x, C16x T1x
C15x, C16x = 0.1 F (0402) T1B = TC1-1-13, 1:1 (Mini-Circuits) for operation <3 GHz, T1A = Johanson Technology 3600BL14M050 for operation from 3 GHz to 4 GHz, Johanson Technology 5400BL15K050 for operation from 4900 MHz to 5800 MHz T3B = TC1-1-13, 1:1 (Mini-Circuits) for operation <3 GHz, T3A = Johanson Technology 3600BL14M050 for operation from 3 GHz to 4 GHz, Johanson Technology 5400BL15K050 for operation from 4900 MHz to 5800 MHz
T3x
RF Input Interface. A 1:1 RF balun that converts the single-ended RF input to differential signal is used.
Rev. 0 | Page 33 of 36
ADL5380
07585-099
Figure 99. Low Band Evaluation Board Top Layer
Figure 101. Low Band Evaluation Board Bottom Layer
07585-100
Figure 100. Midband/High Band Evaluation Board Top Layer Silkscreen
Figure 102. Midband/High Band Evaluation Board Bottom Layer Silkscreen
12 mil.
THERMAL GROUNDING AND EVALUATION BOARD LAYOUT
The package for the ADL5380 features an exposed paddle on the underside that should be well soldered to a low thermal and electrical impedance ground plane. This paddle is typically soldered to an exposed opening in the solder mask on the evaluation board. Figure 103 illustrates the dimensions used in the layout of the ADL5380 footprint on the ADL5380 evaluation board (1 mil = 0.0254 mm). Notice the use of nine via holes on the exposed paddle. These ground vias should be connected to all other ground layers on the evaluation board to maximize heat dissipation from the device package.
25 mil. 23 mil.
82 mil.
12 mil.
19.7 mil. 98.4 mil. 133.8 mil.
07585-105
Figure 103. Dimensions for Evaluation Board Layout for the ADL5380 Package
Under these conditions, the thermal impedance of the ADL5380 was measured to be approximately 30C/W in still air.
Rev. 0 | Page 34 of 36
07585-102
07585-101
ADL5380 OUTLINE DIMENSIONS
4.00 BSC SQ 0.60 MAX 0.60 MAX 0.50 BSC 0.50 0.40 0.30 1.00 0.85 0.80 12 MAX 0.80 MAX 0.65 TYP 2.50 REF 0.05 MAX 0.02 NOM 0.20 REF COPLANARITY 0.08
19 18 EXPOSED PAD 24 1
PIN 1 INDICATOR 2.65 2.50 SQ 2.35
6
PIN 1 INDICATOR
TOP VIEW
3.75 BSC SQ
(BO TTOMVIEW)
13 12
7
0.23 MIN
COMPLIANT TO JEDEC STANDARDS MO-220-VGGD-8
Figure 104. 24-Lead Lead Frame Chip Scale Package [LFCSP_VQ] 4 mm x 4 mm Body, Very Thin Quad (CP-24-3) Dimensions shown in millimeters
ORDERING GUIDE
Model ADL5380ACPZ-R7 1 ADL5380ACPZ-WP1 ADL5380-29A-EVALZ1 ADL5380-30A-EVALZ1
1
Temperature Range -40C to +85C -40C to +85C
Package Description 24-Lead LFCSP_VQ 24-Lead LFCSP_VQ Mid Band (3 GHz to 4 GHz) Evaluation Board Low Band (400 MHz to 3 GHz) Evaluation Board
Package Option CP-24-3 CP-24-3
082908-A
SEATING PLANE
0.30 0.23 0.18
FOR PROPER CONNECTION OF THE EXPOSED PAD, REFER TO THE PIN CONFIGURATION AND FUNCTION DESCRIPTIONS SECTION OF THIS DATA SHEET.
Ordering Quantity 1,500, 7" Tape and Reel 64, Waffle Pack 1 1
Z = RoHS Compliant Part.
Rev. 0 | Page 35 of 36
ADL5380 NOTES
(c)2009 Analog Devices, Inc. All rights reserved. Trademarks and registered trademarks are the property of their respective owners. D07585-0-7/09(0)
Rev. 0 | Page 36 of 36

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